Optical sensor device

ABSTRACT

An optical sensor device includes a light emitter for emitting, to a living body, lights having two wavelengths and blinking at a predetermined frequency, and a light receiver for receiving the lights from the living body. The light receiver outputs first and second detection signals corresponding to the respective wavelengths. A filter circuit extracts, from the first and second detection signals, modulation signals that are obtained with amplitude modulation of signals of the predetermined frequency. The modulation signals are amplified by a post-amplifier and are taken into an arithmetic processing unit after being converted to digital signals by an AD converter. The arithmetic processing unit calculates DC components and AC components of the first and second detection signals by employing the modulation signals converted the digital signals.

CROSS REFERENCE TO RELATED APPLICATIONS

The present application is divisional of U.S. application Ser. No.14/083,904, filed Nov. 19, 2013, which is a continuation ofPCT/JP2012/055967 filed Mar. 8, 2012, which claims priority to JapanesePatent Application No. 2011-113482, filed May 20, 2011, and to JapanesePatent Application No. 2011-113485, filed May 20, 2011, the entirecontents of each of which are incorporated herein by reference.

FIELD OF THE INVENTION

The present invention relates to an optical sensor device including alight emitter and a light receiver.

BACKGROUND OF THE INVENTION

In general, there is known an optical sensor device of the typeincluding a light emitter for emitting light to a measurement target,and a light receiver for receiving the light having been reflected by ortransmitted through a living body (see, e.g., Patent Documents 1 and 2).Patent Document 1 discloses a technique of illuminating a finger or anearlobe of a living body with light emitted from a light emitter,receiving the light having been reflected by or transmitted through theliving body by a light receiver, and detecting a photo-plethysmographicsignal corresponding to the pulse of the living body based on anelectrical signal output from the light receiver. In the technique ofPatent Document 1, an amplifier is connected to the light receiver inorder to amplify the electrical signal obtained through photoelectricconversion performed by the light receiver, and the amplified electricalsignal is input to a processor to execute various types of signalprocessing.

Patent Document 2 discloses a technique of reflecting light from areference light source by a scanning mirror, and receiving the reflectedlight by a detection element. In the technique of Patent Document 2, asignal from the detection element is separated into a direct current(DC) component and an alternating current (AC) component, each of whichis converted to a digital signal by an AD converter.

Patent Document 1: Japanese Unexamined Patent Application PublicationNo. 6-22943

Patent Document 2: Japanese Unexamined Patent Application PublicationNo. 2-13815

In the optical sensor device disclosed in Patent Document 1, theelectrical signal output from the light receiver is amplified by theamplifier. At that time, because extraneous light, such as the sunlight,enters the light receiver in some cases, a noise component attributableto the extraneous light may be superimposed on the electrical signal. Ifthe noise component attributable to the extraneous light becomesexcessive, the amplifier would be saturated and a signal correspondingto the light emitted from the light emitter, such as aphoto-plethysmographic signal, would not be detected correctively.Furthermore, if an amplification degree of the amplifier is reduced toprevent the saturation of the amplifier, a detected signal level wouldbe reduced, thus causing a problem that sensitivity in light receptionand detection accuracy of the photo-plethysmographic signal woulddegrade.

Moreover, conversion to the digital signal by the AD converter isrequired to execute the signal processing in the processor, etc. On thatoccasion, if the noise component attributable to the extraneous light issuperimposed on the electrical signal from the light receiver, theelectrical signal including the noise component is coded and, therefore,resolution of the AD converter has to be sufficiently increased withrespect to a detection signal. For that reason, a dynamic rangeincluding the noise component as well needs to be prepared, thus causinganother problem of raising the manufacturing cost.

On the other hand, Patent Document 2 discloses the technique of, afterseparating the signal from the detection element into the DC componentand the AC component and amplifying them, converting each of thosecomponents to the digital signal by the AD converter. In the disclosedtechnique, however, the DC component and the AC component are separatelysubjected to signal processing, and an amplitude ratio between the DCcomponent and the AC component is not restored to the same ratio as thatwhen the signal has been output from the detection element. Accordingly,the converted digital signals cannot be directly applied to, forexample, the case where the AC component is normalized using the DCcomponent. In addition, in the optical sensor device disclosed in PatentDocument 2, because the DC component and the AC component are detectedin synchronism, the DC component and the AC component have to beconverted to the respective digital signals by separate AD converters.Hence the manufacturing cost tends to increase.

SUMMARY OF THE INVENTION

The present invention has been accomplished in view of the problemsdescribed above, and an object of the present invention is to provide anoptical sensor device, which can reduce the cost, and which allows an ACcomponent to be normalized using a DC component.

(1) Accordingly, the present invention provides an optical sensor devicecomprising a light emitter for emitting light that blinks at apredetermined frequency set in advance, and outputting the light towarda measurement target, a light receiver for receiving the light emittedfrom the light emitter and reflected by or transmitted through themeasurement target, and outputting an electrical signal obtained withphotoelectric conversion of the received light, a filter circuit having,as a pass band, a band that corresponds to a part of the electricalsignal output from the light receiver and that includes thepredetermined frequency of the light emitter, and outputting amodulation signal modulated at the predetermined frequency of the lightemitter, an amplifier for amplifying the modulation signal output fromthe filter circuit, an AD converter for converting the modulationsignal, which is an analog signal after being amplified by theamplifier, to a digital signal, and an arithmetic processing unit forcalculating a DC component and an AC component of the electrical signalbased on the digital signal output from the AD converter.

According to the present invention, the light emitter emits the light atthe predetermined frequency set in advance, and the filter circuitoutputs the modulation signal, which is contained in the electricalsignal output from the light receiver and which is modulated at thepredetermined frequency of the light emitter. The modulation signalcontains a DC component attributable to the light reflected by ortransmitted through the measurement target, and an AC componentcorresponding to temporal changes in absorbance of the measurementtarget. The modulation signal is converted to a digital signal by the ADconverter. Therefore, the arithmetic processing unit can calculate theDC component and the AC component of the electrical signal, which isoutput from the light receiver, based on the modulation signal obtainedas the digital signal. More specifically, for example, the arithmeticprocessing unit can calculate the DC component of the electrical signalby taking a time-average value of the modulation signal, and the ACcomponent of the electrical signal by subtracting the DC component fromthe modulation signal. Hence the AC component can be normalized byemploying the calculated DC component.

Furthermore, since the filter circuit can cut off signals of lowerfrequencies than the predetermined frequency, a cutoff frequency of thefilter circuit can be increased to a value near the predeterminedfrequency of the light emitter. Accordingly, capacitance, for example,used in the filter circuit can be reduced, and reduction in size andcost can be realized.

Moreover, since the modulation signal output from the filter circuit isamplified by the amplifier, the modulation signal can be amplified up toa range near the amplitude range of the AD converter without beingaffected by signals of lower frequencies than the predeterminedfrequency of the light emitter, whereby a signal to noise ratio (S/N)can be stably ensured at a satisfactory level. In addition, since anamplitude range of the modulation signal input to the AD converter isstabilized, resolution per bit of the AD converter is widened. As aresult, a bit width of the AD converter can be reduced, and the cost canalso be reduced.

(2) In the present invention, the light emitter includes two lightemitting elements emitting lights in first and second wavelength bandsdifferent from each other, the light receiver outputs first and secondelectrical signals corresponding respectively to the lights in first andsecond wavelength bands, and the arithmetic processing unit includesabsorbance ratio calculation means for calculating an absorbance ratioof the measurement target based on a ratio of a first ratio between anamplitude of a first AC component and a first DC component, bothobtained from the first electrical signal, to a second ratio between anamplitude of a second AC component and a second DC component, bothobtained from the second electrical signal.

According to the present invention, since the light emitter includes twolight emitting elements outputting the lights in first and secondwavelength bands, and the light receiver outputs the first and secondelectrical signals corresponding respectively to the lights in first andsecond wavelength bands, the absorbance ratio calculation means in thearithmetic processing unit can calculate the absorbance ratio of themeasurement target based on the ratio of the first ratio between theamplitude of the first AC component and the first DC component, bothobtained from the first electrical signal, to the second ratio betweenthe amplitude of the second AC component and the second DC component,both obtained from the second electrical signal. As a result, even whenthe light emission intensity of the light emitter and the lightreception sensitivity of the light receiver are different between thefirst and second wavelength bands, the resultant influence can bereduced.

(3) In the present invention, the arithmetic processing unit includes DCcomponent calculation means for calculating the DC component of theelectrical signal by taking a time-average value of the modulationsignal, and AC component calculation means for calculating the ACcomponent of the electrical signals by excluding the DC component, whichhas been calculated by the DC component calculation means, from themodulation signal.

According to the present invention, the DC component calculation meansin the arithmetic processing unit can calculate the DC component of theelectrical signal by taking the time-average value of the modulationsignal. Moreover, the AC component calculation means in the arithmeticprocessing unit can calculate the AC component of the electrical signalby excluding the DC component, which has been calculated by the DCcomponent calculation means, from the modulation signal.

(4) In the present invention, the DC component calculation means isconstituted by total component calculation means for calculating a totalDC component based on both extraneous light noise and the light from thelight emitter by employing a signal that is contained in the modulationsignal and that is obtained during a light emission on-period of thelight emitter, noise component calculation means for calculating a DCcomponent attributable to the extraneous light noise by employing asignal that is contained in the modulation signal and that is obtainedduring a light emission off-period of the light emitter, and noiseexcluded component calculation means for calculating a DC componentattributable to the light from the light emitter by excluding the DCcomponent, which has been calculated by the noise component calculationmeans, from the DC component having been calculated by the totalcomponent calculation means.

According to the present invention, the total component calculationmeans in the DC component calculation means can calculate the total DCcomponent based on both extraneous light noise and the light from thelight emitter by employing a signal that is contained in the modulationsignal and that is obtained during a light emission on-period of thelight emitter. The noise component calculation means in the DC componentcalculation means can calculate the DC component attributable to theextraneous light noise by employing the signal that is contained in themodulation signal and that is obtained during a light emissionoff-period of the light emitter. The noise excluded componentcalculation means in the DC component calculation means can calculatethe DC component attributable to the light from the light emitter byexcluding the DC component, which has been calculated by the noisecomponent calculation means, from the DC component having beencalculated by the total component calculation means. As a result, thearithmetic processing unit can normalize the AC component by employingthe DC component from which the influence of the extraneous light noisehas been excluded, whereby the absorbance ratio can be obtained withhigher accuracy.

(5) In the present invention, the optical sensor device furthercomprises a separation circuit including the filter circuit andseparating the modulation signal and the DC component of the electricalsignal, the AD converter converts, in addition to the modulation signal,the DC component of the electrical signal, which has been separated bythe separation circuit, to a digital signal, and the arithmeticprocessing unit converts the modulation signal and the DC component ofthe electrical signal in accordance with an amplification factor of theamplifier such that an amplitude ratio between the modulation signal andthe DC component of the electrical signal, both output as the digitalsignals from the AD converter, comes back to a state before theamplification by the amplifier, and calculates the AC component of theelectrical signal based on the modulation signal obtained as the digitalsignal.

According to the present invention, since the electrical signal outputfrom the light receiver is separated into the modulation signalcontaining the AC component and the DC component by the separationcircuit, the modulation signal can be amplified by the amplifierseparately from the DC component of the electrical signal. Theextraneous light noise is mainly superimposed on the DC component, andit is hardly superimposed on the modulation signal containing the ACcomponent. Therefore, a degree of amplification for the modulationsignal can be sufficiently increased with respect to the signal range ofthe AD converter that is a component of a digital processing unit. As aresult, the signal to noise ratio (S/N) can be improved and stabilized.

Moreover, since the arithmetic processing unit converts the modulationsignal and the DC component of the electrical signal, which are obtainedas the digital signals, such that their amplitudes take the same ratioas that before the amplification by the amplifier, it is possible torestore the amplitude ratio between the DC component of the electricalsignal and the modulation signal in the state just output from the lightreceiver. In addition, since the AC component of the electrical signalis calculated based on the modulation signal obtained as the digitalsignal, the AC component can be normalized by employing the DC componentand the AC component after being restored.

(6) In the present invention, the arithmetic processing unit includesnoise component calculation means for calculating the DC componentattributable to the extraneous light noise based on a signal that iscontained in the DC component of the electrical signal and that isobtained during a light emission off-period of the light emitter.

Here, the DC component of the electrical signal having been separated bythe separation circuit contains components attributable to both theextraneous light noise and the light from the light emitter. Since thearithmetic processing unit can calculate the DC component attributableto the extraneous light noise by the noise component calculation means,the DC component attributable to the extraneous light noise can beexcluded from the DC component output from the separation circuit. Thus,the AC component can be normalized by employing the DC component fromwhich an influence of the extraneous light noise has been excluded,whereby the absorbance ratio can be determined with higher accuracy.

(7) The present invention further provides an optical sensor devicecomprising a light emitter for emitting light toward a measurementtarget, and a light receiver for receiving the light emitted from thelight emitter and reflected by or transmitted through the measurementtarget, and outputting an electrical signal obtained with photoelectricconversion of the received light, wherein the optical sensor devicefurther comprises a separation circuit for separating the electricalsignal output from the light receiver into a DC component and an ACcomponent, an amplification circuit for amplifying the DC component andthe AC component, which have been separated by the separation circuit,at separate amplification factors, an AD converter for converting the DCcomponent and the AC component, analog signals amplified by theamplification circuit, to digital signals, and an arithmetic processingunit for restoring the DC component and the AC component of theelectrical signal by converting the DC component and the AC componentoutput as the digital signals from the AD converter in accordance withthe separate amplification factors of the amplification circuit suchthat an amplitude ratio between the DC component and the AC componentoutput as the digital signals comes back to a state before theamplification by the amplification circuit.

According to the present invention, the electrical signal output fromthe light receiver is separated into the DC component and the ACcomponent by the separation circuit, and the DC component and the ACcomponent having been separated from each other are amplified at theseparate amplification factors by the amplification circuit. Therefore,saturation of the amplification circuit due to the extraneous lightnoise can be suppressed by reducing the amplification factor of the DCcomponent. On the other hand, the extraneous light noise is mainlysuperimposed on the DC component, and it is hardly superimposed on theAC component. Therefore, a degree of amplification for the AC componentcan be sufficiently increased with respect to the signal range of the ADconverter that is a component of the digital processing unit. As aresult, the signal to noise ratio (S/N) can be improved and stabilized.

Moreover, since the DC component and the AC component can be bothamplified up to a range near the amplitude range of the AD converter, asignal to noise ratio (S/N) can be stably ensured at a satisfactorylevel for each of the DC component and the AC component. In addition,since an amplitude range of the signal input to the AD converter isstabilized, resolution per bit of the AD converter is widened. As aresult, a bit width of the AD converter can be reduced, and the cost canalso be reduced.

Furthermore, since the arithmetic processing unit converts the DCcomponent and the AC component, which are obtained as the digitalsignals, such that their amplitudes take the same ratio as that beforethe amplification by the amplification circuit, it is possible torestore the amplitude ratio between the DC component and the ACcomponent of the electrical signal in the state just output from thelight receiver. Accordingly, the AC component can be normalized, forexample, by employing the DC component and the AC component after beingrestored.

In the present invention, the light emitter may be configured to emitlight blinking at a predetermined frequency set in advance. Theseparation circuit may be configured to have, as a pass band, a bandincluding the predetermined frequency of the light emitter, and tooutput the AC component modulated at the predetermined frequency of thelight emitter

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is an overall block diagram of an optical sensor device accordingto a first embodiment.

FIG. 2 is a flowchart of a processing program executed by an arithmeticprocessing unit in FIG. 1.

FIG. 3 is an explanatory view illustrating first and second detectionsignals and modulation signals in the optical sensor device in FIG. 1.

FIG. 4 is an overall block diagram of an optical sensor device accordingto a second embodiment.

FIG. 5 is a flowchart of a processing program executed by an arithmeticprocessing unit in FIG. 4.

FIG. 6 is an explanatory view illustrating a state where a DC componentand an AC component are separated from each of first and seconddetection signals and are amplified by the optical sensor device in FIG.4.

FIG. 7 is an overall block diagram of an optical sensor device accordingto a comparative example.

FIG. 8 is an overall block diagram of an optical sensor device accordingto a third embodiment.

FIG. 9 is a flowchart of a processing program executed by an arithmeticprocessing unit in FIG. 8.

FIG. 10 is an explanatory view illustrating a state where a DC componentand an AC component are separated from each of first and seconddetection signals and are amplified by the optical sensor device in FIG.8.

DETAILED DESCRIPTION OF THE EXEMPLARY EMBODIMENTS

Optical sensor devices according to embodiments of the present inventionwill be described in detail below with reference to the accompanyingdrawings.

FIG. 1 illustrates an optical sensor device 1 according to a firstembodiment. The optical sensor device 1 detects, for example, aphoto-plethysmographic signal (pulse wave signal) corresponding to thepulse of a living body B that is a measurement target.

A light emitter 2 is constituted by first and second light emittingelements 3 and 4 that output lights in first and second wavelength bandsdifferent from each other, respectively. The first and second lightemitting elements 3 and 4 are each constituted by, e.g., a lightemitting diode (LED). Herein, the first light emitting element 3 emits,e.g., red light in a band of 700 nm, and the second light emittingelement 4 emits, e.g., infrared light in a band of 900 nm.

First and second drive circuits 5 and 6 are connected to the first andsecond light emitting elements 3 and 4, respectively. The first andsecond light emitting elements 3 and 4 emit lights blinking inaccordance with drive currents supplied from the first and second drivecircuits 5 and 6, respectively.

Herein, the first drive circuit 5 supplies a drive current that ispulse-modulated at a predetermined frequency f set in advance. Thepredetermined frequency f is set to a frequency higher than a signalfrequency (e.g., about several Hz) of the photo-plethysmographic signal.Preferably, the predetermined frequency f is set to a value (e.g., aboutseveral hundreds Hz) higher than the signal frequency of thephoto-plethysmographic signal by ten or more times within a range inwhich a processing circuit 12 is able to execute processing.

In addition, the predetermined frequency f is set to a value (e.g.,f=100 Hz) sufficiently lower than the changeover cycle (e.g., 400 Hz) ofan AD converter 14 such that conversion to a digital signal can beperformed by the AD converter 14.

The second drive circuit 6 also has substantially the same configurationas that of the first drive circuit 5. Thus, the second drive circuit 6supplies a drive current, which is pulse-modulated at the samepredetermined frequency f as that in the first drive circuit 5, to thesecond light emitting element 4, thereby causing the second lightemitting element 4 to emit blinking light. On that occasion, forexample, the first and second light emitting elements 3 and 4alternately emit the lights at timings different from each other.

However, when a light receiver 7 can separately receive the lights inthe first and second wavelength bands, the first and second lightemitting elements 3 and 4 may be configured to emit the lights at thesame timing in synchronism. The first and second light emitting elements3 and 4 may be each constituted using a vertical cavity surface emittinglaser (VCSEL) or a laser diode (LD).

The light receiver 7 is constituted by, e.g., a light receiving element,such as a photodiode (PD). The light receiver 7 receives an opticalsignal and outputs it after photoelectric conversion to an electricalsignal, e.g., a current signal or a voltage signal. More specifically,the light receiver 7 receives the lights emitted from the light emittingelements 3 and 4 and reflected by or transmitted through the living bodyB, converts the received lights to first and second detection signals S1and S2 in the form of electrical signals, and outputs the detectionsignals S1 and S2 to a preamplifier 8. Here, the first detection signalS1 is a signal corresponding to the light in the first wavelength band,and the second detection signal S2 is a signal corresponding to thelight in the second wavelength band.

The light receiving element constituting the light receiver 7 may be aphototransistor, as another example. The light receiver 7 may beconstituted using a single light receiving element, or using a pluralityof light receiving elements, which receive lights in differentwavelength bands by employing optical filters, for example.

The preamplifier 8 is constituted using, e.g., an operational amplifier.An input terminal of the preamplifier 8 is connected to the lightreceiver 7. The preamplifier 8 amplifies the detection signals S1 andS2, output from the light receiver 7, at an amplification factor Gx andoutputs the amplified signals to a filter circuit 9.

The filter circuit 9 is constituted by a capacitor 9A, which serves as acoupling capacitor connected between the preamplifier 8 and apost-amplifier 10. The filter circuit 9 functions as a high-pass filterallowing passage of signals of frequencies, equal to or higher than thepredetermined frequency f at which the first and second light emittingelements 3 and 4 emit the blinking lights. The cutoff frequency of thefilter circuit 9 is set to a value as high as possible within a rangeallowing the signals of the predetermined frequency f to passtherethrough.

Because the light emitter 2 emits the lights blinking at thepredetermined frequency f, the first and second detection signals S1 andS2 are each a signal obtained with amplitude modulation of the signal ofthe predetermined frequency f. On that occasion, because the capacitor9A cuts off signals of lower frequencies than the predeterminedfrequency f, the filter circuit 9 outputs modulation signals S1 m and S2m that are obtained respectively from the first and second detectionsignals S1 and S2 through amplitude modulation at the predeterminedfrequency f.

The post-amplifier 10 is an amplifier for amplifying the modulationsignals S1 m and S2 m. The post-amplifier 10 is constituted using anoperational amplifier, for example, and it constitutes an amplificationcircuit 11 in combination with the preamplifier 8. The post-amplifier 10is connected to the output side of the filter circuit 9. Thepost-amplifier 10 amplifies the first and second modulation signals S1 mand S2 m at an amplification factor Gy, and then outputs first andsecond modulation signals S1M and S2M after the amplification. Here, anamplification factor Gm of the first and second modulation signals S1Mand S2M is set by both the preamplifier 8 and the post-amplifier 10, andthe amplification factor Gm is equal to the product of the amplificationfactor Gx and the amplification factor Gy (i.e., Gm=Gx×Gy). Thus, theamplification factors Gx and Gy of the preamplifier 8 and thepost-amplifier 10 are set such that an amplitude range of each of thefirst and second modulation signals S1M and S2M has a value comparableto that of an input range of the AD converter 14.

The processing circuit 12 is mainly constituted by a multiplexer 13, anAD converter 14, and an arithmetic processing unit 15.

The multiplexer 13 connects the post-amplifier 10 to the AD converter14. Accordingly, the first and second modulation signals S1M and S2Moutput from the post-amplifier 10 are input to the AD converter 14through the multiplexer 13. For example, when the first and second lightemitting elements 3 and 4 are driven to emit the lights alternately, thefirst and second modulation signals S1M and S2M can be input, as aseries of time-divided signals, to the AD converter 14 in the form of asingle unit. In such a case, the post-amplifier 10 may be directlyconnected to the AD converter 14 by omitting the multiplexer 13.

The AD converter 14 converts the first and second modulation signals S1Mand S2M from analog signals to digital signals. At that time, the ADconverter 14 converts, for example, only plus-side values of the firstand second modulation signals S1M and S2M to digital signals. Moreover,the first and second modulation signals S1M and S2M are set by thepreamplifier 8 and the post-amplifier 10 to values comparable to theinput range of the AD converter 14. Therefore, the AD converter 14 canconvert the first and second modulation signals S1M and S2M to thedigital signals by employing the entire input range thereof.

The arithmetic processing unit 15 is constituted by a microcomputer, forexample. By executing a processing program illustrated in FIG. 2, thearithmetic processing unit 15 calculates respective DC components S1 dand S2 d and respective AC components S1 a and S2 a of the first andsecond detection signals S1 and S2 based on the first and secondmodulation signals S1M and S2M output from the AD converter 14, andfurther determines an absorbance ratio R12 of the living body B. Theprocessing program illustrated in FIG. 2 is executed, for example, eachtime the first and second modulation signals S1M and S2M are updated bythe AD converter 14.

In more detail, the arithmetic processing unit 15 executes a DCcomponent calculation process illustrated in steps 1 to 3 of FIG. 2, andcalculates the respective DC components S1 d and S2 d a of the first andsecond detection signals S1 and S2 based on the first and secondmodulation signals S1M and S2M.

The first and second modulation signals S1M and S2M contain DCcomponents, which are attributable to extraneous light noise, inaddition to the DC components of the lights emitted from the lightemitting elements 3 and 4 and reflected by or transmitted through theliving body B. In view of the above-mentioned point, in a totalcomponent calculation process illustrated in step 1, DC components S1don and S2 don attributable to both the extraneous light noise and thelights from the light emitting elements 3 and 4 are calculated byextracting, from the first and second modulation signals S1M and S2M,signals obtained during light emission on-periods of the light emittingelements 3 and 4, and by calculating respective time-average values ofthe extracted signals. At that time, each time-average value iscalculated for a time corresponding to at least one cycle (e.g., about 1sec) of the photo-plethysmographic signal, preferably two or morecycles, but the time is as short as possible within such a condition.

Next, in a noise component calculation process illustrated in step 2, DCcomponents S1 doff and S2 doff attributable to the extraneous lightnoise are calculated by extracting, from the first and second modulationsignals S1M and S2M, signals obtained during light emission off-periodsof the light emitting elements 3 and 4, and by calculating respectivetime-average values of the extracted signals.

Next, in a noise excluded component calculation process illustrated instep 3, the DC components S1 d and S2 d attributable to the lights fromthe light emitter 2 are calculated by excluding the DC components S1doff and S2 doff, calculated in step 2, from the DC components S1 donand S2 don calculated in step 1, respectively.

Next, in an AC component calculation process illustrated in step 4, theAC components S1 a and S2 a are calculated by extracting, from the firstand second modulation signals S1M and S2M, signals obtained during lightemission on-periods of the light emitting elements 3 and 4, and bysubtracting the DC components S1 don and S2 don, calculated in step 1,from the extracted signals.

Next, in step 5, a normalized signal calculation process is executed tonormalize amplitudes ΔS1 a and ΔS2 a of the AC components S1 a and S2 aby employing the DC components S1 d and S2 d, respectively. Morespecifically, normalized signals S10 and S20 are calculated as first andsecond ratios by dividing the amplitudes ΔS1 a and ΔS2 a by the DCcomponents S1 d and S2 d, respectively, in accordance with the followingformula 1.

$\begin{matrix}{{{S\; 10} = \frac{\Delta\; S\; 1a}{S\; 1d}}{{S\; 20} = \frac{\Delta\; S\; 2a}{S\; 2d}}} & \left\lbrack {{Math}.\mspace{14mu} 1} \right\rbrack\end{matrix}$

Next, in step 6, an absorbance ratio calculation process is executed tocalculate the absorbance ratio R12 by employing the normalized signalsS10 and S20. More specifically, the absorbance ratio R12 is calculatedby dividing the normalized signal S10 corresponding to the firstwavelength by the normalized signal S20 corresponding to the secondwavelength in accordance with the following formula 2.

$\begin{matrix}{{R\; 12} = \frac{S\; 10}{S\; 20}} & \left\lbrack {{Math}.\mspace{14mu} 2} \right\rbrack\end{matrix}$

The arithmetic processing unit 15 may produce, in addition to theabsorbance ratio R12, biological information, such as a degree of oxygensaturation, acceleration pulse wave, and pulse fluctuation, based on thefirst and second detection signals S1 and S2. Furthermore, thearithmetic processing unit 15 is connected to the first and second drivecircuits 5 and 6 to establish synchronism between the light emission bythe first and second light emitting elements 3 and 4 and the lightreception by the light receiver 7 based on the operations of the firstand second drive circuits 5 and 6.

The optical sensor device 1 according to the first embodiment of thepresent invention is constituted as described above, and the operationof the optical sensor device 1 is described below.

First, a switch (not illustrated) of the optical sensor device 1 isturned on in a state that the light emitter 2 and the light receiver 7are disposed near the living body B. Upon the turning-on of the switch,the first and second light emitting elements 3 and 4 of the lightemitter 2 output the lights in the first and second wavelength bands,respectively. The light receiver 7 receives the emitted lights afterbeing reflected by or transmitted through the living body B, and outputsthe first and second detection signals S1 and S2 corresponding to thefirst and second wavelength bands, respectively. As illustrated in FIG.3, the modulation signals S1 m and S2 m are extracted from the first andsecond detection signals S1 and S2, respectively, by the filter circuit9 and are input to the processing circuit 12. In the processing circuit12, the modulation signals S1M and S2M are converted to the digitalsignals by the AD converter 14, and the DC components S1 d and S2 d andthe AC components S1 a and S2 a are calculated by the arithmeticprocessing unit 15. Other various processes are also executed by thearithmetic processing unit 15.

Because the optical sensor device is configured here such that the lightemitter 2 emits the lights at the predetermined frequency f and thefilter circuit 9 outputs the modulation signals S1 m and S2 m modulatedat the predetermined frequency f of the light emitter 2, the cutofffrequency of the filter circuit 9 can be set to a higher value, and thecapacitance of the capacitor 9A can be reduced.

To explain in more detail, the photo-plethysmographic signal is alow-frequency signal of about several Hz corresponding to the pulse ofthe living body. To separate the photo-plethysmographic signal,therefore, the cutoff frequency is to be set as low as about several Hz,and a capacitor having a large capacity of, e.g., about several hundredsμF is required. In contrast, in the first embodiment, the filter circuit9 is just required to allow passage of signals of the predeterminedfrequency f, which is higher than the frequency of thephoto-plethysmographic signal, in order to separate the modulationsignals S1 m and S2 m modulated at the predetermined frequency f of thelight emitter 2. Therefore, the cutoff frequency of the filter circuit 9can be set to a higher value, and the capacitance of the capacitor 9Acan be reduced to be smaller than 1 μF, for example. As a result,miniaturization and cost-reduction can be realized.

Moreover, the modulation signals S1M and S2M resulting from amplifyingthe modulation signals S1 m and S2 m contain not only the DC componentsS1 d and S2 d attributable to the lights from the light emittingelements 3 and 4, but also the AC components S1 a and S2 a attributableto the photo-plethysmographic signal. The DC components S1 d and S2 dcan be determined from respective time-average values of the modulationsignals S1M and S2M. In the case of taking the time-average values ofsignals that are contained in the modulation signals S1M and S2M andthat are obtained during the light emission on-periods of the lightemitting elements 3 and 4, the time-average values include the componentattributable to the extraneous light noise in addition to the componentscorresponding to the lights from the light emitting elements 3 and 4.Accordingly, in the first embodiment, of the modulation signals S1M andS2M, the DC components S1 doff and S2 doff resulting from time-averagingthe signals obtained during the light emission off-periods of the lightemitting elements 3 and 4 are subtracted from the DC components S1 donand S2 don resulting from time-averaging the signals obtained during thelight emission on-periods of the light emitting elements 3 and 4,respectively. As a result, the DC components S1 d and S2 d attributableto the lights from the light emitting elements 3 and 4 can be calculatedby excluding the component attributable to the extraneous light noise.

Furthermore, the arithmetic processing unit 15 can calculate theabsorbance ratio R12 based on a ratio of the normalized signal S10,which is obtained as a first ratio of the amplitude ΔS1 a of a first ACcomponent S1 a and a first DC component S1 d, to the normalized signalS20, which is obtained as a second ratio of the amplitude ΔS2 a of asecond AC component S2 a and a second DC component S2 d. As a result,even when the light emission intensity of the light emitter 2 and thelight reception sensitivity of the light receiver 7 are differentbetween the first and second wavelength bands, the resultant influencecan be reduced. In addition, since the amplitudes ΔS1 a and ΔS2 a of theAC components S1 a and S2 a are normalized by employing the DCcomponents S1 d and S2 d obtained after removing the influence of theextraneous light noise, the absorbance ratio R12 of the living body Bcan be determined with high accuracy.

The modulation signals S1M and S2M are signals amplified at theamplification factor Gm by the preamplifier 8 and the post-amplifier 10.On that occasion, since a DC noise component, etc., excluded from themodulation signals S1M and S2M by the filter circuit 9, they undergo asmaller influence of the extraneous light noise than the first andsecond detection signals S1 and S2. Therefore, saturation of both theamplifiers 8 and 10 caused by the extraneous light noise can besuppressed. Moreover, since respective amplitude ranges of themodulation signals S1 m and S2 m are stabilized, respective amplituderanges of the modulation signals S1M and S2M after the amplification canbe each set to a value comparable to that of the input range of the ADconverter 14. Accordingly, a signal to noise ratio (S/N) can be stablyensured at a satisfactory level. In addition, since minimum resolutionrepresenting resolution per the least significant bit of the ADconverter 14 is improved, a bit width of the AD converter 14 can bereduced, and the cost can also be reduced.

In the first embodiment described above, steps 1 to 3 in FIG. 2represent a practical example of DC component calculation means. Step 1in FIG. 2 represents a practical example of total component calculationmeans. Step 2 in FIG. 2 represents a practical example of noisecomponent calculation means. Step 3 in FIG. 2 represents a practicalexample of noise excluded component calculation means. Step 4 in FIG. 2represents a practical example of AC component calculation means. Step 6in FIG. 2 represents a practical example of absorbance ratio calculationmeans.

FIG. 4 illustrates an optical sensor device 21 according to a secondembodiment. The optical sensor device 21 detects, for example, aphoto-plethysmographic signal (pulse wave signal) corresponding to thepulse of a living body B as a measurement target.

A light emitter 22 is constituted by first and second light emittingelements 23 and 24 that output lights in first and second wavelengthbands different from each other, respectively. The first and secondlight emitting elements 23 and 24 are each constituted by, e.g., a lightemitting diode (LED). Herein, the first light emitting element 23 emits,e.g., red light in a band of 700 nm, and the second light emittingelement 24 emits, e.g., infrared light in a band of 900 nm.

First and second drive circuits 25 and 26 are connected to the first andsecond light emitting elements 23 and 24, respectively. The first andsecond light emitting elements 23 and 24 emit continuously lastinglights or intermittently blanking lights in accordance with drivecurrents supplied from the first and second drive circuits 25 and 26,respectively.

Herein, the first and second light emitting elements 23 and 24 mayalternately emit the lights in a time-division manner, for example.Alternatively, when a light receiver 27 can separately receive thelights in the first and second wavelength bands, the first and secondlight emitting elements 23 and 24 may emit the lights at the same timingin synchronism. The first and second light emitting elements 23 and 24may be each constituted using a vertical cavity surface emitting laser(VCSEL) or a laser diode (LD).

The light receiver 27 is constituted by, e.g., a light receivingelement, such as a photodiode (PD). The light receiver 27 receives anoptical signal and outputs it after photoelectric conversion to anelectrical signal, e.g., a current signal or a voltage signal. Morespecifically, the light receiver 27 receives the lights emitted from thelight emitting elements 23 and 24 and reflected by or transmittedthrough the living body B, converts the received lights to first andsecond detection signals S1 and S2 in the form of electrical signals,and outputs the detection signals S1 and S2 to a preamplifier 28. Here,the first detection signal S1 is a signal corresponding to the light inthe first wavelength band, and the second detection signal S2 is asignal corresponding to the light in the second wavelength band.

The light receiving element constituting the light receiver 27 may be aphototransistor, as another example. The light receiver 27 may beconstituted using a single light receiving element, or using a pluralityof light receiving elements, which receive lights in differentwavelength bands by employing optical filters, for example.

The preamplifier 28 is constituted using, e.g., an operationalamplifier. An input terminal of the preamplifier 28 is connected to thelight receiver 27. The preamplifier 28 amplifies the detection signalsS1 and S2, output from the light receiver 27, at an amplification factorGx and outputs the amplified signals to a separation circuit 29.

The separation circuit 29 is constituted by first and second branchlines 30 and 31, which are connected in parallel to an output terminalof the preamplifier 28, and by a filter circuit 32, which functions as ahigh-pass filter connected to an intermediate point of the second branchline 31. The filter circuit 32 is constituted by a capacitor 32A thatserves as a coupling capacitor connected between the preamplifier 28 anda post-amplifier 33.

The first branch line 30 transmits the first and second detectionsignals S1 and S2 output from the preamplifier 28, as they are,including the DC components S1 d and S2 d. Therefore, the first branchline 30 serves as a DC component transmission path for transmitting theDC components S1 d and S2 d of the first and second detection signals S1and S2.

On the other hand, the capacitor 32A functioning as a coupling capacitoris disposed in the second branch line 31. Because the DC components S1 dand S2 d of the first and second detection signals S1 and S2 are blockedby the capacitor 32A, the second branch line 31 serves as an ACcomponent transmission path for transmitting the AC components S1 a andS2 a of the first and second detection signals S1 and S2. Thecapacitance of the capacitor 32A is set depending on frequencies of theAC components S1 a and S2 a of the first and second detection signals S1and S2, which are to be passed through the capacitor 32A.

When the first and second AC components S1 a and S2 a are sufficientlysmaller (e.g., 1/10 or less) than the first and second DC components S1d and S2 d, the first and second detection signals S1 and S2 becomesubstantially the same signals as the DC components S1 d and S2 d,respectively. Therefore, the first branch line 30 transmits the firstand second detection signals S1 and S2 as they are. On the contrary,when the first and second AC components S1 a and S2 a are comparable tothe first and second DC components S1 d and S2 d, or when the first andsecond AC components S1 a and S2 a are larger than the first and secondDC components S1 d and S2 d, a low-pass filter, e.g., an integrator, maybe connected to the first branch line 30.

The post-amplifier 33 is an amplifier for amplifying the first andsecond AC components S1 a and S2 a. The post-amplifier 33 is connectedto the second branch line 31 on the output side of the capacitor 32A.The post-amplifier 33 amplifies the first and second AC components S1 aand S2 a of the first and second detection signals S1 and S2 at anamplification factor Gy, and then outputs first and second AC componentsS1A and S2A after the amplification. The post-amplifier 33 isconstituted using an operational amplifier, for example, and itconstitutes an amplification circuit 34 in combination with thepreamplifier 28. Here, an amplification factor Gd of the first andsecond DC components S1 d and S2 d of the first and second detectionsignals S1 and S2 is set by the preamplifier 28, and the amplificationfactor Gd is equal to the amplification factor Gx (i.e., Gd=Gx). On theother hand, an amplification factor Ga of the first and second ACcomponents S1A and S2A of the first and second detection signals S1 andS2 is set by both the preamplifier 28 and the post-amplifier 33, and theamplification factor Ga is equal to the product of the amplificationfactor Gx and the amplification factor Gy (i.e., Ga=Gx×Gy). Thus, theamplification circuit 34 amplifies the DC components S1 d and S2 d andthe AC components S1 a and S2 a of the first and second detectionsignals S1 and S2, which are separated by the separation circuit 29, atthe separate amplification factors Gd and Ga, respectively.

When the AC components S1 a and S2 a of the first and second detectionsignals S1 and S2 are photo-plethysmographic signals, the AC componentsS1 a and S2 a changing depending on the blood flow in the living body Bare smaller than the DC components S1 d and S2 d corresponding to thereflected or transmitted lights directly obtained from the living bodyB. In the amplification circuit 34, therefore, the amplification factorGa for the AC components S1 a and S2 a is set to be larger than theamplification factor Gd for the DC components S1 d and S2 d such thatthe amplitudes of those components are set to values comparable to theamplitude range of an AD converter 37 described below.

The processing circuit 35 is mainly constituted by a multiplexer 36, theAD converter 37, and an arithmetic processing unit 38.

The multiplexer 36 is connectable to the first branch line 30 of theseparation circuit 29, and to the second branch line 31 thereof at adownstream position of the post-amplifier 33. The multiplexer 36alternately connects the first and second branch lines 30 and 31 to theAD converter 37 in a time-division manner, for example.

When the multiplexer 36 is connected to the first branch line 30, the ADconverter 37 converts the DC components S1 d and S2 d of the first andsecond detection signals S1 and S2 from analog signals to digitalsignals, and when the multiplexer 36 is connected to the second branchline 31, the AD converter 37 converts the AC components S1A and S2A ofthe first and second detection signals S1 and S2 from analog signals todigital signals. At that time, the DC components S1 d and S2 d and theAC components S1A and S2A of the first and second detection signals S1and S2 are each set by the amplification circuit 34 to a valuecomparable to the input range of the AD converter 37. Therefore, the ADconverter 37 can convert the DC components S1 d and S2 d and the ACcomponents S1A and S2A to the digital signals by employing the entireinput range thereof.

The first and second detection signals S1 and S2 are directly input, asthe DC components S1 d and S2 d, to the AD converter 37. When the ACcomponents S1 a and S2 a are sufficiently smaller (e.g., 1/10 or less)than the DC components S1 d and S2 d and are comparable to theresolution of the AD converter 37, the AC components S1 a and S2 a areremoved when the DC components S1 d and S2 d are converted to thedigital signals by the AD converter 37. On the other hand, when the ACcomponents S1 a and S2 a are so large as not negligible, it ispreferable to previously remove the AC components S1 a and S2 acontained in the DC components S1 d and S2 d by employing a low-passfilter, or to determine time-average values of the DC components S1 dand S2 d having been converted to the digital signals.

The arithmetic processing unit 38 is constituted by a microcomputer, forexample. By executing a processing program illustrated in FIG. 5, thearithmetic processing unit 38 restores the first and second detectionsignals S1 and S2 before the amplification based on the DC components S1d and S2 d and the AC components S1A and S2A, which are output from theAD converter 37, and further determines an absorbance ratio R12 of theliving body B. The processing program illustrated in FIG. 5 is executed,for example, each time the digital signals of the DC components S1 d andS2 d and the AC components S1A and S2A are updated by the AD converter37.

In more detail, the arithmetic processing unit 38 executes a ratiorestoration process, illustrated in step 11 of FIG. 5, by converting theDC components S1 d and S2 d and the AC components S1A and S2A of thefirst and second detection signals S1 and S2 based on the amplificationfactors Gd and Ga such that respective amplitudes of those componentsare restored to have the same ratios as those before the amplificationby the amplification circuit 34. On that occasion, the amplificationfactors Gd and Ga are different from each other by the amplificationfactor Gy of the post-amplifier 33, and the amplitudes of the ACcomponents S1A and S2A input to the arithmetic processing unit 38 arelarger in amplitude than that of the DC components S1 d and S2 d by theamplification factor Gy of the post-amplifier 33. In view of such adifference, the arithmetic processing unit 38 calculates restored ACcomponents S1 ar and S2 ar by dividing the AC components S1A and S2A bythe amplification factor Gy as expressed in the following formula 3. Asa result, the DC components S1 d and S2 d and the AC components S1 arand S2 ar are restored to have the ratios between their amplitudes(i.e., the amplitude ratios) before the amplification.

$\begin{matrix}{{{S\; 1{ar}} = \frac{\;{S\; 1A}}{Gy}}{{S\; 2{ar}} = \frac{\;{S\; 2A}}{Gy}}} & \left\lbrack {{Math}.\mspace{14mu} 3} \right\rbrack\end{matrix}$

Next, in step 12, a combining process of combining the restored ACcomponents S1 ar and S2 ar with the DC components S1 d and S2 d,respectively, is executed to obtain first and second restoration signalsSR1 and SR2 resulting from restoring the first and second detectionsignals S1 and S2 before the amplification. More specifically, the firstand second restoration signals SR1 and SR2 are calculated by adding therestored AC components S1 ar and S2 ar to the DC components S1 d and S2d, respectively, as expressed in the following formula 4.SR1=S1d+S1arSR2=S2d+S2ar  [Math. 4]

Next, in step 13, a normalized signal calculation process is executed tonormalize respective amplitudes ΔS1 ar and ΔS2 ar of the AC componentsS1 ar and S2 ar by employing the DC components S1 d and S2 d,respectively. Here, the amplitudes ΔS1 ar and ΔS2 ar are obtained byrestoring respective amplitudes ΔS1A and ΔS2A of the AC components S1Aand S2A after the amplification to the states before the amplification,i.e., by dividing the amplitudes ΔS1A and ΔS2A by the amplificationfactor Gy. Normalized signals S10 and S20 are calculated as the firstand second ratios by dividing the amplitudes ΔS1 ar and ΔS2 ar by the DCcomponents S1 d and S2 d, respectively, in accordance with the followingformula 5.

$\begin{matrix}{{{S\; 10} = \frac{\;{\Delta\; S\; 1{ar}}}{S\; 1d}}{{S\; 20} = \frac{\;{\Delta\; S\; 2{ar}}}{S\; 2d}}} & \left\lbrack {{Math}.\mspace{14mu} 5} \right\rbrack\end{matrix}$

Next, in step 14, an absorbance ratio calculation process is executed tocalculate the absorbance ratio R12 by employing the normalized signalsS10 and S20. More specifically, the absorbance ratio R12 is calculatedby dividing the normalized signal S10 corresponding to the firstwavelength by the normalized signal S20 corresponding to the secondwavelength in accordance with the above-described formula 2.

The arithmetic processing unit 38 may produce, in addition to theabsorbance ratio R12, biological information, such as a degree of oxygensaturation, acceleration pulse wave, and pulse fluctuation, based on thefirst and second detection signals S1 and S2. Furthermore, thearithmetic processing unit 38 is connected to the first and second drivecircuits 25 and 26 to establish synchronism between the light emissionby the first and second light emitting elements 23 and 24 and the lightreception by the light receiver 27 based on the operations of the firstand second drive circuits 25 and 26.

The optical sensor device 21 according to the second embodiment of thepresent invention is constituted as described above, and the operationof the optical sensor device 21 is described below.

First, a switch (not illustrated) of the optical sensor device 21 isturned on in a state that the light emitter 22 and the light receiver 27are disposed near the living body B. Upon the turning-on of the switch,the first and second light emitting elements 23 and 24 of the lightemitter 22 output the lights in the first and second wavelength bands,respectively. The light receiver 27 receives the emitted lights afterbeing reflected by or transmitted through the living body B, and outputsthe first and second detection signals S1 and S2 corresponding to thefirst and second wavelength bands, respectively. The first and seconddetection signals S1 and S2 are separated by the separation circuit 29into the DC components S1 d and S2 d and the AC components S1A and S2A,as illustrated in FIG. 6, which are then input to the processing circuit35 in the separated state. In the processing circuit 35, the DCcomponents S1 d and S2 d and the AC components S1A and S2A are convertedto the digital signals by the AD converter 37, and various processes areexecuted by the arithmetic processing unit 38.

Herein, the DC components S1 d and S2 d and the AC components S1A andS2A are amplified respectively at the separate amplification factors Gdand Ga by the amplification circuit 34. Accordingly, the respectiveamplitudes of the DC components S1 d and S2 d and the AC components S1Aand S2A can be set to be comparable to each other, and those amplitudescan be set to values comparable to the amplitude range of the ADconverter 37. As a result, minimum resolution representing resolutionper the least significant bit of the AD converter 37 is improved.

The foregoing point is described in more detail with reference to FIG. 7representing a comparative example. An optical sensor device 41according to the comparative example, illustrated in FIG. 7, includes alight emitter 42, a drive circuit 43, a light receiver 44, an amplifier45, and a processing circuit 46. The processing circuit 46 isconstituted by an AD converter 47 and an arithmetic processing unit 48.In the optical sensor device 41, a DC component Sd and an AC componentSa of a detection signal S are amplified at the same amplificationfactor G by the amplifier 45.

It is here assumed that the DC component Sd is 0.01 [V], the ACcomponent Sa is about 1/10 (0.001 [V]) of the DC component Sd, and theDC component Sd is increased about 10 times (i.e., to 0.1 [V]) by theextraneous light noise. In such a case, assuming a maximum voltage levelof the AD converter 47 to be 1 [V], the amplification factor G of theamplifier 45 is about 10 at maximum.

Furthermore, an amplitude ratio of the AC component Sa to the DCcomponent Sd is not changed between the input side and the output sideof the amplifier 45, the AC component Sa cannot be detected with highaccuracy unless the resolution of the AD converter 47 is set to be high.However, the maximum voltage level of the AD converter 47 is determineddepending on a maximum value of the DC component Sd attributable to theextraneous light noise. Accordingly, when the resolution of the ADconverter 47 is set to 10 bits, minimum resolution is, e.g., about 488[μ:V/LSB] for each of the DC component Sd and the AC component Sa.

In contrast, in the optical sensor device 21 according to the secondembodiment, the DC components S1 d and S2 d and the AC components S1Aand S2A of the detection signals S1 and S2 are amplified respectively atthe separate amplification factors Gd and Ga, for example, by employingthe post-amplifier 33. Even in the case where the amplitudes of the DCcomponents S1 d and S2 d and the AC components S1 a and S2 a and theinfluence of the extraneous light noise on those amplitudes in the stagebefore the amplification are the same as in the comparative exampledescribed above, therefore, assuming the amplification factor Gd of theDC components S1 d and S2 d to be 1 and the amplification factor Ga ofthe AC components S1 a and S2 a to be 10, both the components can beinput to the AD converter 37 with their amplitudes matched to the samevalue of 0.01 [V]. As a result, even if the DC components S1 d and S2 dare increased about 10 times (0.1 [V]) by the extraneous light noise,the maximum voltage level of the AD converter 37 can be reduced to 0.1[V].

In addition, the amplification factor Ga of the AC components S1 a andS2 a is set to be larger than the amplification factor Gd of the DCcomponents S1 d and S2 d such that the amplitudes of the AC componentsS1A and S2A after the amplification come close to the amplitude range ofthe AD converter 37. Therefore, even when the resolution of the ADconverter 37 is reduced to 8 bits, the minimum resolution for the ACcomponents S1A and S2A is increased to, e.g., about 19.53 [μ:V/LSB]. Inthis regard, the minimum resolution for the DC components S1 d and S2 dis, e.g., about 19.53 [μV/LSB] when there is no influence of theextraneous light noise, and is, e.g., about 195.31 [μV/LSB] when thereis an influence of the extraneous light noise.

According to the second embodiment, as described above, the minimumresolution of the AD converter 37 can be improved, and an AD converterhaving lower resolution can be used as the AD converter 37. It is hencepossible to reduce the power consumption and the manufacturing cost.

Thus, in the optical sensor device 21 according to the secondembodiment, the first and second detection signals S1 and S2 output fromthe light receiver 27 are separated into the DC components S1 d and S2 dand the AC components S1 a and S2 a by the separation circuit 29, andthe DC components S1 d and S2 d and the AC components S1A and S2A, afterbeing separated from each other, are amplified at the separateamplification factors Gd and Ga by the amplification circuit 34,respectively. Therefore, the saturation of the amplification circuit 34due to the extraneous light noise can be suppressed by reducing theamplification factor Gd of the DC components S1 d and S2 d. On the otherhand, since other signals than the photo-plethysmographic signal arehardly superimposed on the AC components S1 a and S2 a, theamplification factor Ga for the AC components S1A and S2A can besufficiently increased with respect to the signal range of the ADconverter 37 that is a component of a digital processing unit. As aresult, the signal to noise ratio (S/N) can be improved and stabilized.

Furthermore, since the DC components S1 d and S2 d and the AC componentsS1A and S2A can be all amplified up to ranges near the amplitude rangeof the AD converter 37, the signal to noise ratio (S/N) can be stablyensured at a satisfactory level. In addition, since the amplitude rangeof each signal input to the AD converter 37 is stabilized, voltageresolution of the AD converter 37 per bit is widened. Accordingly, thebit width of the AD converter 37 can be reduced and cost reduction canbe realized.

Moreover, since the arithmetic processing unit 38 executes theconversion such that the respective amplitudes of the DC components S1 dand S2 d and the AC components S1A and S2A of the digital signals takethe same ratios as those before the amplification by the amplificationcircuit 34, the DC components S1 d and S2 d and the AC components S1 arand S2 ar can be restored at the same amplitude ratio as that when thosecomponents are output from the light receiver 27. Therefore, theamplitudes ΔS1 ar and ΔS2 ar of the AC components S1 ar and S2 ar can benormalized respectively by employing the DC components S1 d and S2 d andthe AC components S1 ar and S2 ar after being restored, for example.

Accordingly, the arithmetic processing unit 38 can calculate theabsorbance ratio R12 based on a ratio of the normalized signal S10,which is obtained as a first ratio of the amplitude ΔS1 ar of a first ACcomponent S1 ar and a first DC component S1 d, to the normalized signalS20, which is obtained as a second ratio of the amplitude ΔS2 ar of asecond AC component S2 ar and a second DC component S2 d. As a result,even when the light emission intensity of the light emitting elements 23and 24 and the light reception sensitivity of the light receiver 27 aredifferent between the first and second wavelength bands, the resultantinfluence can be reduced and the detection accuracy of the absorbanceratio R12 can be increased.

Next, FIG. 8 illustrates a third embodiment of the present invention.The third embodiment is featured in that the light emitter emits lightat a predetermined frequency set in advance, and that the separationcircuit has, as a passage band, a band including the predeterminedfrequency of the light emitter and outputs an AC component modulated atthe predetermined frequency of the light emitter. It is to be notedthat, in the third embodiment, the same constituent elements as those inthe second embodiment are denoted by the same reference symbols, anddescription of those constituent elements is omitted.

An optical sensor device 51 includes, substantially as in the opticalsensor device 21 according to the second embodiment, the light emitter22, first and second drive circuits 52 and 53, the light receiver 27, aseparation circuit 54, an the amplification circuit 34, and a processingcircuit 56.

Substantially like the first drive circuit 25 in the second embodiment,the first drive circuit 52 is connected to an arithmetic processing unit57 in the processing circuit 56, and it supplies a drive current to thefirst light emitting element 23, thereby causing the first lightemitting element 23 to emit blinking light. Here, the first drivecircuit 52 supplies the drive current that is pulse-modulated at thepredetermined frequency f set in advance. The predetermined frequency fis set to a frequency higher than a signal frequency (e.g., aboutseveral Hz) of the photo-plethysmographic signal. Preferably, thepredetermined frequency f is set to a value (e.g., about severalhundreds Hz) higher than the signal frequency of thephoto-plethysmographic signal by ten or more times within a range inwhich the processing circuit 56 is able to execute processing.

In addition, the predetermined frequency f is set to a value (e.g.,f=100 Hz) sufficiently lower than the changeover cycle (e.g., 400 Hz) ofthe AD converter 37 such that conversion to a digital signal can beperformed by the AD converter 37.

The second drive circuit 53 also has substantially the sameconfiguration as that of the first drive circuit 52. Thus, the seconddrive circuit 53 supplies a drive current, which is pulse-modulated atthe same predetermined frequency f as that in the first drive circuit52, to the second light emitting element 24, thereby causing the secondlight emitting element 24 to emit blinking light. On that occasion, forexample, the first and second light emitting elements 23 and 24 may emitthe lights at the same timing in synchronism, or may alternately emitthe lights at timings different from each other.

The separation circuit 54 also has substantially the same configurationas that of the separation circuit 29 in the second embodiment. Thus, theseparation circuit 54 is constituted by first and second branch lines 30and 31, which are connected in parallel to an output terminal of thepreamplifier 28, and by a filter circuit 55, which functions as ahigh-pass filter connected to an intermediate point of the second branchline 31. The filter circuit 55 is constituted by a capacitor 55A thatserves as a coupling capacitor connected between the preamplifier 28 andthe post-amplifier 33.

Here, the capacitance of the capacitor 55A is set to a value allowingpassage of signals of relatively high frequencies, including the signalshaving the drive frequency of the light emitting elements 23 and 24.More specifically, the cutoff frequency of the high-pass filter,constituted by the capacitor 55A, is set to a value as high as possiblewithin a range allowing the signal of the predetermined frequency f setfor the first and second drive circuits 52 and 53 to pass therethrough.

Because the light emitter 22 emits the lights blinking at thepredetermined frequency f, the first and second detection signals S1 andS2 are each a signal obtained with amplitude modulation of the signal ofthe predetermined frequency f. On that occasion, because the capacitor55A cuts off signals of lower frequencies than the predeterminedfrequency f, the filter circuit 55 outputs the first and second ACcomponents S1 am and S2 am, as modulation signals, which are obtainedrespectively from the first and second detection signals S1 and S2through amplitude modulation at the predetermined frequency f. Thepost-amplifier 33 is an amplifier for amplifying the first and second ACcomponents S1 m and S2 m which are the modulation signals. Accordingly,the first and second AC components S1 am and S2 am, both transferredthrough the second branch line 31, are input to the processing circuit56 after being amplified respectively to first and second AC componentsS1Am and S2Am by the post-amplifier 33.

Substantially like the processing circuit 35 in the second embodiment,the processing circuit 56 is mainly constituted by the multiplexer 36,the AD converter 37, and the arithmetic processing unit 57.

Here, the first and second DC components S1 d and S2 d and the first andsecond AC components S1Am and S2Am are input to the AD converter 37 inthe processing circuit 56 through the multiplexer 36, and the ADconverter 37 converts the DC components S1 d and S2 d and the ACcomponents S1Am and S2Am to digital signals. At that time, the ADconverter 37 converts only plus-side values of the AC components S1Amand S2Am to digital signals, for example. The DC components S1 d and S2d and the AC components S1Am and S2Am, having been converted to thedigital signals, are input to the arithmetic processing unit 57 that isconstituted by, e.g., a microcomputer.

By executing a processing program illustrated in FIG. 9, the arithmeticprocessing unit 57 restores the first and second detection signals S1and S2 before the amplification based on the DC components S1 d and S2 dand the AC components S1Am and S2Am, which are output from the ADconverter 37, and further determines an absorbance ratio R12 of theliving body B. In other words, the arithmetic processing unit 57converts the DC components S1 d and S2 d and the AC components S1Am andS2Am by employing the amplification factor Gy of the post-amplifier 33such that amplitude ratios between the DC components S1 d and S2 d andthe AC components S1Am and S2Am come back to the states before theamplification by the post-amplifier 33.

In more detail, the arithmetic processing unit 57 executes a ratiorestoration process, illustrated in step 21 of FIG. 9. In step 21, thearithmetic processing unit 57 converts the DC components S1 d and S2 dand the AC components S1Am and S2Am of the first and second detectionsignals S1 and S2 based on the amplification factors Gd and Ga such thatrespective amplitudes of those components are restored to have the sameratios as those before the amplification by the amplification circuit34. More specifically, the arithmetic processing unit 57 executesarithmetic operations, similar to the above-described formula 3, tocalculate restored AC components S1 ar and S2 ar by dividing the ACcomponents S1Am and S2Am by the amplification factor Gy.

Next, in step 22, a combining process of combining the restored ACcomponents S1 ar and S2 ar with the DC components S1 d and S2 d,respectively, is executed. More specifically, the arithmetic processingunit 57 executes arithmetic operations, similar to the above-describedformula 4, to obtain first and second restoration signals SR1 and SR2,which are resulted from restoring the first and second detection signalsS1 and S2 before the amplification, by adding the restored AC componentsS1 ar and S2 ar to the DC components S1 d and S2 d, respectively.

As illustrated in FIG. 10, the AC components S1 ar and S2 ar obtainedafter amplification correction of the AC components S1Am and S2Amcontain the components attributable to the reflected or transmittedlights directly obtained from the living body B. To avoid thosecomponents from being superimposed doubly, the first and secondrestoration signals SR1 and SR2 may be calculated by adding the restoredAC components S1 ar and S2 ar to DC components S1 doff and S2 doff,which are obtained during the light emission off-periods of the emittingelements 23 and 24 and which are contained in the DC components S1 d andS2 d, respectively.

Next, in step 23, a noise component calculation process is executed toobtain the DC components S1 doff and S2 doff attributable to theextraneous light noise by employing the detection signals S1 and S2during the light emission off-periods of the light emitter 22. Morespecifically, as illustrated in FIG. 10, when the light emittingelements 23 and 24 do not emit the lights, DC components S1 d 0 and S2 d0 attributable to the lights emitted from the light emitting elements 23and 24 are not detected, and only the DC components S1 doff and S2 doffattributable to the extraneous light noise are detected. Therefore, theDC components S1 doff and S2 doff attributable to the extraneous lightnoise can be obtained by extracting, from the DC components S1 d and S2d, signals obtained during the light emission off-periods of the lightemitting elements 23 and 24.

Next, in step 24, a noise excluded component calculation process isexecuted to obtain the DC components S1 d 0 and S2 d 0 excluding theextraneous light noise. More specifically, the detection signals S1 andS2 during the light emission on-periods of the light emitter 22 areextracted to obtain DC components S1 don and S2 don attributable to notonly the extraneous light noise, but also the lights from the lightemitting elements 23 the 24, and the DC components S1 doff and S2 doffattributable to the extraneous light noise are subtracted from the DCcomponents S1 don and S2 don. As a result, the DC components S1 d 0 andS2 d 0 from which the extraneous light noise has been excluded arecalculated.

Next, in step 25, a normalized signal calculation process is executed tonormalize the amplitudes ΔS1 ar and ΔS2 ar of the AC components S1 arand S2 ar by employing the DC components S1 d 0 and S2 d 0,respectively. Here, the amplitudes ΔS1 ar and ΔS2 ar are ones obtainedby restoring the amplitudes ΔS1A and ΔS2A of the AC components S1Am andS2Am after the amplification to the states before the amplification. Thenormalized signals S10 and S20 are calculated as the first and secondratios by dividing the amplitudes ΔS1 ar and ΔS2 ar by the DC componentsS1 d 0 and S2 d 0, respectively, in accordance with the followingformula 6.

$\begin{matrix}{{{S\; 10} = \frac{\;{\Delta\; S\; 1{ar}}}{S\; 1d\; 0}}{{S\; 20} = \frac{\;{\Delta\; S\; 2{ar}}\;}{{S\; 2d\; 0}\;}}} & \left\lbrack {{Math}.\mspace{14mu} 6} \right\rbrack\end{matrix}$

While, in step 25, the normalized signals S10 and S20 are obtained usingthe DC components S1 d 0 and S2 d 0, the normalized signals S10 and S20may be obtained based on only the AC components S1Am and S2Am. In such acase, as seen from FIG. 10, values S1A0 and S2A0 corresponding to the DCcomponents excluding the extraneous light noise can be calculated bysubtracting, for the AC components S1Am and S2Am, the AC componentsS1Aoff and S2Aoff during the light emission off-periods fromtime-average values of the AC components S1Aon and S2Aon during thelight emission on-periods of the light emitting elements 23 and 24,respectively. By dividing the amplitudes ΔS1A and ΔS2A of the ACcomponents S1Am and S2Am by the values S1A0 and S2A0, therefore, theamplitudes ΔS1A and ΔS2A can be normalized and the normalized signalsS10 and S20 can be obtained.

Next, in step 26, an absorbance ratio calculation process is executed tocalculate the absorbance ratio R12 by employing the normalized signalsS10 and S20. More specifically, the absorbance ratio R12 is calculatedby dividing the normalized signal S10 corresponding to the firstwavelength by the normalized signal S20 corresponding to the secondwavelength in accordance with the above-described formula 2.

Thus, the third embodiment can also provide similar advantageous effectsto those in the second embodiment. According to the third embodiment,particularly, since the light emitter 22 emits the lights at thepredetermined frequency f and the separation circuit 54 outputs the ACcomponents S1 am and S2 am modulated at the predetermined frequency f ofthe light emitter 22, the cutoff frequency of the separation circuit 54can be set to a higher value and the capacitance of the capacitor 55Acan be reduced.

To explain in more detail, the photo-plethysmographic signal is alow-frequency signal of about several Hz corresponding to the pulse ofthe living body. To separate the photo-plethysmographic signal,therefore, the cutoff frequency is to be as low as about several Hz, anda capacitor having a large capacitance of, e.g., about several hundredsμF is required. In contrast, in the third embodiment, the separationcircuit 54 is just required to allow passage of signals of thepredetermined frequency f, which is higher than the frequency of thephoto-plethysmographic signal, in order to separate the AC components S1am and S2 am modulated at the predetermined frequency f of the lightemitter 22. Therefore, the cutoff frequency of the separation circuit 54can be set to a higher value, and the capacitance of the capacitor 55Acan be reduced to be smaller than 1 μF, for example. As a result,reduction in size and cost can be realized.

Furthermore, the DC components S1 doff and S2 doff attributable to theextraneous light noise alone can be extracted by employing digitalsignal data of the DC components S1 d and S2 d during the light emissionoff-periods. Thus, since the DC components S1 doff and S2 doffattributable to the extraneous light noise can be excluded respectivelyfrom the detected DC components S1 d and S2 d, the amplitudes ΔS1 ar andΔS2 ar of the AC components S1 ar and S2 ar can be normalized withoutsuffering from the influence of the extraneous light noise. As a result,the absorbance ratio R12 of the living body B can be obtained with highaccuracy.

In the second and third embodiments described above, step 11 in FIG. 5and step 21 in FIG. 9 represent practical examples of ratio restorationmeans. Step 14 in FIG. 5 and step 26 in FIG. 9 represent practicalexamples of absorbance ratio calculation means. Step 23 in FIG. 9represents a practical example of noise component calculation means.

While, in each of the above-described embodiments, the light emitters 2and 22 are each configured to emit the lights of two differentwavelengths, they may be each configured to emit light of one wavelengthor lights of three or more wavelengths.

Moreover, the foregoing embodiments have been each described above inconnection with an example in which the present invention is applied tothe optical sensor device 1, 21 or 51 for detecting thephoto-plethysmographic signal of the living body B. However, applicationfields of the present invention are not limited to that type of opticalsensor device, and the present invention can be applied to various typesof optical sensor devices for detecting lights reflected by ortransmitted through measurement targets.

REFERENCE SIGNS LIST

-   -   1, 21, 51 optical sensor devices    -   2, 22 light emitters    -   3, 4, 23, 24 light emitting elements    -   7, 27 light receivers    -   9, 32, 55 filter circuits    -   10, 33 post-amplifiers (amplifiers)    -   11, 34 amplification circuits    -   14, 37 AD converters    -   15, 38, 57 arithmetic processing units    -   29, 54 separation circuits

The invention claimed is:
 1. An optical sensor device, comprising: alight emitter configured to periodically emit light at a predeterminedfrequency toward a measurement target; a light receiver configured todetect at least one of reflected light and diffused light from themeasurement target, and to output a modulated electrical signal based onthe detected light; a filter circuit configured to filter the modulatedelectrical signal at the predetermined frequency and to output amodulation signal; an amplifier configured to amplify the modulationsignal; an AD converter configured to convert the modulation signal to adigital signal; an arithmetic processing unit coupled to the ADconverter and configured to calculate a DC component and an AC componentof the electrical signal based on the digital signal; and a separationcircuit including the filter circuit and configured to separate themodulation signal and the DC component of the electrical signal, whereinthe AD converter is further configured to convert the DC component ofthe electrical signal to a DC component digital signal, and wherein thearithmetic processing unit is further configured to convert themodulation signal and the DC component digital signal based on anamplification factor of the amplifier, such that an amplitude ratiobetween the modulation signal and the DC component digital signalreaches a state before the amplification by the amplifier, and tocalculate the AC component of the electrical signal based on themodulation signal.
 2. The optical sensor device according to claim 1,wherein the arithmetic processing unit is further configured tocalculate the DC component attributable to extraneous light noise basedon a signal contained in the DC component of the electrical signal andobtained during an off-period of the light emitter.
 3. An optical sensordevice, comprising: a light emitter configured to emit light toward ameasurement target; a light receiver configured to detect at least oneof reflected light and diffused light from the measurement target, andoutput an electrical signal based on the detected light; a separationcircuit configured to separate the electrical signal into a DC componentand an AC component; an amplification circuit configured to amplify theDC component and the AC component, at first and second amplificationfactors, respectively; an AD converter configured to convert the DCcomponent and the AC component to first and second digital signals,respectively; and an arithmetic processing unit configured to restorethe DC component and the AC component of the electrical signal byconverting the DC component and the AC component output as the first andsecond digital signals such that an amplitude ratio between the DCcomponent and the AC component output as the digital signals obtains astate before the amplification by the amplification circuit.
 4. Anoptical sensing method, comprising: emitting light, by a light emitter,at a predetermined frequency towards a measurement target; detecting, bya light receiver, at least one of reflected light and diffused lightfrom the measurement target; outputting, by the light receiver, amodulated electrical signal based on the detected light; filtering, by afilter circuit, the modulated electrical signal at the predeterminedfrequency; outputting, by the filter circuit, a modulation signalcorresponding to the electrical signal; amplifying, by an amplifier, themodulation signal; converting, by an AD converter, the amplifiedmodulation signal to a digital signal; calculating, by a processor, a DCcomponent and an AC component of the electrical signal based on thedigital signal; separating, by a separation circuit including the filtercircuit, the modulation signal and the DC component of the electricalsignal; converting, by the AD converter, the DC component of theelectrical signal to a DC component digital signal; converting, by theprocessor, the modulation signal and the DC component digital signalbased on an amplification factor of the amplifier, such that anamplitude ratio between the modulation signal and the DC componentdigital signal reaches a state before the amplification by theamplifier; and calculating, by the processor, the AC component of theelectrical signal based on the modulation signal.
 5. The optical sensingmethod according to claim 4, further comprising calculating, by theprocessor, the DC component attributable to extraneous light noise basedon a signal contained in the DC component of the electrical signal andobtained during an off-period of the light emitter.